Millimeter-wave antenna measurements with the HP8510 network analyzer

Millimeter-wave antenna measurements with the HP8510

network analyzer

Citation for published version (APA):

Beeckman, P. A. (1985). Millimeter-wave antenna measurements with the HP8510 network analyzer. (EUT

report. E, Fac. of Electrical Engineering; Vol. 85-E-149). Technische Hogeschool Eindhoven.

Document status and date:

Published: 01/01/1985

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, 0 1

T

\tE'

Millimeterwave antenna

measurements with the

HP851 0

network analyzer

by

P.A. Beeckman

EUT Report 85-E-149

ISBN 90-6144-149-8

ISSN 0167-9708

EINDHOVEN UNIVERSITY OF TECHNOLOGY Department of Electrical Engineering

Eindhoven The Netherlands

MILLI~ETER-WAVE

ANTENNA MEASUREMENTS

WITH THE HP8510 NETWORK ANALYZER

by

P.A. 8eeckman

EUT Report 85-E-149

ISBN 90-6144-149-8

ISSN 0167-9708

Coden, TEUEDE

Eindhoven

May

1985

8506255··

T

_{. . n.!:,..,}

~

....

IN

_DHO\lEN

.

,

I'

CIP-GEGEVENS KONINKLIJKE BIBLIOTHEEK, DEN HAAG

Beeckman, P.A.

Millimeter-wave antenna measurements with the HP9510 network analyzer / by P.A. Beeckman. - Eindhoven:

University of Technology. - Fig. - (Eindhoven University

of Technology research reports / Department of Electrical

Engineering, ISSN 0167-9708, 85-E-149)

Met lit. opg., reg.

ISBN 90-6144-149-8

SISO 669.2 UDC 621.396.67.08 UGI 650

ABSTRACT

The possibilities of performing millimeter-wave antenne measurements

by using the HP8510 network analyzer are investigated. The configuration and operation of the modified mm-wave test setup are described. The results of antenna measurements, performed at30, 35 and 39 GHz with two different types of antennas are discussed. Special attention is paid to the dynamic range performance of the system. Finally a method is described to use the time domain feature of the analyzer for aperture

field analysis.

Beeckman, P.A.

MILLIMETER-WAVE ANTENNA MEASUREMENTS WITH THE HP8510 NETWORK ANALYZER.

Department of Electrical Engineering, Eindhoven University of

Technology (Netherlands), 1985. EUT Report 85-E-149

Address of the author: P.A. Beeckman,

Group Electromagnetism and Circuit Theory, Department of Electrical Engineering, Eindhoven University of Technology,

P.O. Box 513,

5600 MB EINDHOVEN, The Netherlands

CONTENTS PAGE

Abstract .. ... .. i i i

1. Introduction... 1

2. System description... . . . .. .. .. . .. . . .. .. .. .. .. .. . .. . .. .. .. .. .. .. . .. . .. . . . .. . . .. .. .. 2

3. System operation... . . . .. . . .. . . . .. . .. .. .. .. .. .. . . . . .. . .. . . . .. . . . . 4

4. Aperture field analysis by using the time domain feature.... 8

5. Conclusions... 12

References. .. . . . . . . .. .. .. . . . .. . .. . . .. . . . . . .. . . . . . . .. . . . . . . .. .. . . . . .. . 12

Acknowledgement.. . . . .. .. .. .. .. .. . . .. . . . . . . .. .. . . . . .. . . . .. . . . . .. . . .. .. . .. . 12

1. INTRODUCTION

The HP8510 network analyzer may be configured to make vector measurements at millimeter-wave frequencies. The procedures how to configure the mm-wave test system are described in [1]. This rom-mm-wave test system is very

suitable for measuring the reflection and transmission properties of microwave devices. If, however, the device under test is an antenna-test range, then the mm-wave test system must be modified and consequently some aspects of the performance of the test system must be reconsidered.

In this report we will discuss the modified rom-wave test system which was used to perform antenna measurements. In antenna measurements the radiation properties of an antenna as a function of its angular position are recorded; for instance the co- and cross-polar far-field patterns. This type of measurements differs from the microwave-device measurements which are employed usually, such as reflection and transmission measurements as a function of the frequency.

When performing antenna measurements the HP8510A and the mm-wave test system will operate at one frequency. It will be shown that i t is possible to measure the far-field of an antenna as a function of the rotation angle and display the result in the frequency domain of the network analyzer.

Thus the frequency axis of the network analyzer in the frequency domain will be used as the angular position axis of the far-field antenna pattern. If now the time domain capability of the analyzer if used, then i t is possible to perform a Fourier transform on the recorded far-field data. For one-dimansional antennas (line sources, linear arrays etc.) the Fourier transform of the far-field ,is proportional to the aperture field distri-bution of the antenna.

By

experiments we will show that the time domain feature of the analyzer can be used succesfully for analysis of aperture field distributions of antennas.

In this report also the dynamic range of the antenna mm-wave test system will be discussed. Since accurate measurement of low sidelobe levels becomes more and more important, the dynamic range of an antenna-test facility must be considered carefully.

~.

SYSTEM DESCRIPTION

---A simplified block diagram for the mm-wave antenna measurement system is shown in figure 1. The main components of the system are:

*

an HP8510A network analyzer

*

two HP8340A synthesized sweepers

• a HP9000 series 200 controller

The test signal is generated by one of the synthesized sweepers. After amplification, the output signal drives a frequency multiplier whose output is at the mm-wave signal frequency. This signal is then

applied to the compact antenna-test range (CATR).

The CATR consists of two parabolic cylindrical reflectors of which the focal lines are placed perpendicular to each other [3]. When this two-reflector system is fed by a spherical source a planar wave front is produced in the test zone of the anechoic room. When a test antenna

is rotated in this test zone, its radiation properties can be measured under far-field conditions.

The signal detected by the test antenna (RFb) and a portion of the

signal which was applied to the CATR feed (RFa) are applied to two

harmonic mixers. The other synthesized sweeper serves as the local oscillator (LO) for each of the harmonic mixers. The rnm-wave signal

and the appropriate LO harmonic are offset by exactly 20 MHz. The

20 MHz IF signals are applied directly to the IF detector of the HP8510A

analyzer (a1 and b1). When the parameter Sll (ratio of b1 and a1) is

selected, then the radiation properties of the test antenna can be measured.

The network analyzer and the two synthesized sweepers are under command of a controller via the HP-IB bus.

More details on the system configuration (power levels, hardware,

Software

The mm-wave measurement system is controlled by the HP8510a-KOl software which is written in HP9000 series 200 enhanced Basic.

The software performs two principal functions: stimulus control and calibration kit definitions.

The type of antenna measurements we are interested in, are performed at one frequency. Therefore the calibration features of the HP8510 system will not be considered here.

Test antennas

For the experiments two different types of antennas were used: 1. A focal plane parabolic reflector antenna.

(diameter 0.6

m,

f/D

=

0.25).

This test antenna was used for measurements at 35 and 39 GHz. The gain of this antenna at 100% efficiency is approximately given by

*

47 dB at 35 GHz

*

48 dB at 39 GHz

2. A pill box antenna (aperture dimensions 0.06 x 1.2m).

This antenna was tested at 30 GHz. The pill-box antenna may be considered as a linear (one-dimensional) antenna. Therefore this antenna is useful to demonstrate the aperture analysis method.

3. SYSTEM OPERATION

---The system operation of the millimeter wave test system is described extensively in [1]. Therefore, here only the problems concerning the test system modified for application of antenna measurements will be discribed.

The stimulus control was performed by the software. For all the antenna measurements the following stimulus settings were selected:

- operating waveguide band WR28 (25.5 - 40.0 GHz) - frequency CW mode (span

=

0 GHz)

- source power

=

0 dEm

- number of points

=

401 - avering factor

=

128

The test antenna was mounted on a positioner which was controlled by a positioner programmer. The measurements were performed while the antenna

was moved in the azimuth plane from -20 to +20 degrees. The main beam

direction was approximately 0 degrees. The angular speed of the positioner was selected in such a way, that the sweep time (401 pOints and averaging factor 128

=

about 80 seconds) and the antenna scan time coincide.

The data acquisition and the antenna positioner programmer were synchro-nized at -20 degrees. In this way the antenna radiation pattern was recorded as a function of the angular position. So the sweep axis

(frequency axis) of the analyzer was used as an angular axis!

Calibration

The antenna measurements were performed at a constant frequency. Consequently calibration measurements in order to compensate for non-ideal frequency responses, impedance mismatches etc. were not necessary. However, in order to discuss the dynamic range of the system i t is useful to perform some simple calibration measurements.

We consider the CATR as u DUT (figure 2) with the input waveguide of the CATR feed as an input port (calibration plane 1) and the output of the

First a THRU-measurement of the CATR system was done as a function of frequency by connecting the calibration planes 1 and 2 together (figure 2). The result of this THRU-measurement is used to calibrate our sensitivity measurements. The variation of the transmitted power is mainly caused by

the variation of the power level at the input test port (between -8 dEm

and

a

dBm) due to the ALC loop and the used multiplier [1].

Then the sensitivity level P of the antenna test system was measured.

sens

This was done by covering the CATR feed by metallic sheet and, in

additional, by absorber. The power level measured at test port 2 relative

to the level at port 1 is given in figure 3. We observe that the average

noise level

(=

sensitivity level) is about -100 dB for the frequency range

of 26.5 to 40.0 GHz. The input power level varies from

a

dBm to -8 dBm, so the absolute noise level at the mixer output varies from -100 dBm to -108 dBm, which is consistent with the specifications: mixer output noise

level -108 dBm at 1 kHz bandwidth. Further we observe from figure 3 that

the sensitivity level can be lowered about 5 dB by increasing the averaging

factor from 128 to 2048.

Now the operating dynamic range

(DR)

of the rom-wave test system will be

investigated. The most important parameters, which influence the dynamic range of the measurement system are:

*

*

*

*

*

*

the input power Pl at test port 1 the efficiency factor of the CATR:

n

cr

the test zone efficiency factor, which is the ratio of the projected

apertures of the

CATR

and the

TA·

n

=

s /s

.

tz

ta

cr

the efficiency of the test antenna:

n

ta

conversion loss of the mixer ncl

noise level of the harmonic mixer output at test port 2 (p ). sens

In figure 4 the impact of these parameters on the output power is illustrated. It is readily seen that the received power level P2 can be written as:

P2

_{n ·n ·n ·n}

_l·P1

When the sensitivity P of the mixer is known then the dynamic range sens

DR can be written as:

DR = n _cr ·n _tz ·n _ta .n I.P1/P _{c sens} (2)

Some typical values for the parameters in 2 which influence the DR are

- input power P1

=

0 dBm

- CATR efficiency _ncr 0.1 (-10 dB)

- test zone efficiency _n

tz

s Is

ta cr = 0.07 (-11 dB),

Sta 0.28m2 and S _cr = 3.9 m2

- test antenna efficiency _n

ta 0.5 (-3 dB)

- conversion loss mixer _n

cl -24 dB

- sensitivity level P = -100 dB below P1 (figure 3)

sens

Using these levels in relation 2 gives the following estimate for the DR:

(3 ) -10 -11 -3 -24 +0 +100 -52 dB

This estimate is verified experimentally by using the 0.6 m paraboloid

antenna at 35 and 39 GHz.

First the received power of the antenna in

bore sight

direction was measured

during a half sweep period (level

=

0 dB). Then the CATR feed was covered

by metallic sheet and absorber in order to measure the noise level during the rest of the sweep period. The results (figure 5) show that the noise level is about 60 dB below the received power of the antenna in boresight direction. So a dynamic range of 60 dB can be obtained when measuring the 0.6 m paraboloid antenna by using this mm-wave test system configuration.

This is consistent with the specifications of the dynamic range given in [1] (80 dB). The difference of 20 dB is caused by the CATR and test zone

efficiencies n a n d n (see relations 2 and 3).

cr tz

In order to illustrate the rom-wave system measurement abilities a few measurements with the 0.6 m parabolic reflector antenna are described.

The results of the far-field radiation patterns at 35 GHz and 39 GHz

are shown

in

the figures 6 and 7.

Because of the good CATR test zone amplitude and phase characteristics

at these frequencies [3], deep nulls, low sidelobe levels and low

crosspolar level can be detected

if

available.

Indeed we observe from the results (figures 6 and 7) that the dynamic

range of the system is sufficient to be able to measure the lower power

levels accurately.

4. APERTURE FIELD ANALYSIS BY USING THE TIME DOMAIN FEATURE

---Introduction

From antenna theory it is known that the far-field of an antenna is

proportional

which is the

to an angular plane-wave spectrum function A{k ,k ),

x

y

two-dimensional Fouriertransform of the aperture field distribution E (x,y) of the antenna:

a

A(k ,k )

x y

where

K,y

are aperture coordinates

+

k y)

y

dxdy

(4)

k,k are the x- and y-components of the wavenumbervector k,

x y

for small angular displacements these components can be written as

k

ksin

t; (t;

=

azimuth angle)

x

k

=

ksin 11

(11

=

elevation angle)

y

If the antenna is moved only in the azimuth plane, then the far-field

spectrum function simplifies into

A (k ,0)

x

00 00 -21

f

[-21

f

E

(x,y)dy

1

1f

_{_00}

1f

_{_00}

a

jk

x e x dx

The Fourier transform of the far-field spectrum A(k ,0) is

x

p(x)

E

(x,y)dy

a

-jk

x =

f

A

(k

,0)

e

x dk

x

x

-'"

(5) (6)

The function P(x) can be interpreted as a projection of the aperture

field on the x-axis. It is evident that when the aperture distribution

j H

one-dimensional then the projection function P (x) is equal to the

aperture field distribution at y = 0:

E

(x,y) .21f.6(y).e(x)

a

then P(x)

= e(x) and with A(k ,0)

x

-jk

x

P(x)

=

e(x)

=

f

a(k ) e

x

dk

x

x

-00

• a(k ) we find

x

(7)

From this analysis we see that a one-dimensional Fouriertransform relation exists between the aperture field distribution e(x) and the far-field spectrum function a(k ) for the case the aperture field

x

distribution is one-dimensional (7). For a two-dimensional aperture distribution the 1-D Fourier transform of the function a(k ) is a

x

projection of the two-dimensional aperture function (6).

If on the HP8510 "a time domain option is available then the data in the

frequency domain can be transformed to the time domain by performing a chirp-Z Fast Fourier transform. For network analysis this time domain option is very attractive (e.g. for reflection coefficient measurements) .

The method how to measure an antenna radiation pattern by using the frequency domain of the HP8510 was described in the previous chapter. It also has been shown that the Fourier transform of the far-field pattern of an antenna is meaningful (6 and 7). Therefore it would be nice,

if

the time domain feature of the analyzer could be used as an "aperture domain" for analysis of antenna aperture field distributions.

Indeed it appeared to be possible to transform the measured far-field data by using the time domain feature of the analyzer. To do this the network analyzer had to be cheated by some proper stimulus settings.

First of all the antenna far-field was measured at one frequency

(SPAN

=

0 GHz). After this sweep a SPAN ~ 0 had to be selected, so that the PASSBAND TIME DOMAIN could be used.

If positive START and STOP frequencies were selected then the phase in the time domain increased very rapidly. This was caused by the fact that the main beam of the antenna pattern corresponds with a positive frequency. And according to the Fourier transform properties a shift in the frequency domain corresponds to a constant phase factor in the time domain.

Fortunately, it was possible to select a proper negative START frequency for solving this problem.

Another problem was the assignment of absolute values to the distance

coordinate of our "aperture domain". The aperture distribution is a function of the distance, so i t would ne neat to assign scale values in meters to the horizontal axis of the "aperture domain".

By

applying the properties of a discrete Fourier transform, one can derive

the following relation between the sample distance

in the angular domain

(6~)

and the span X in the aperture domain:

X = 180A!(1T.6~) (m)

where

11~

=

A/N; A

N

span in angular domain (degrees) number of samples

(8)

For instance a sample distance of 0.1 degree at 30 GHz gives an aperture

span X of about 5.7 m.

In the time domain of the analyzer also a distance in meters is displayed

when using gating or the markers. This distance Xt is related to the time

T (in nanoseconds) as follows:

Xt

=

0.3 T

(m)

If this distance indication is used for our aperture domain, then we have

to select a frequency span F (in GHz) of

F

N

0.3 N

T

X

A.1T.f

180

(GHz)

(9)

where A

=

the angular span in degrees over which the antenna was rotated

f

=

frequency

in GHz

at

which the antenna was measured.

For

f

= 30 GHz

a~d

A

=

40 degr a frequency span of 21 GHz must be chosen

in order to obtain horizontal scale values which agree with the real distances in the

aperture

domain.

In the figures 8, 9 and 10 some results are shown of measurements with

the 1.2 m pill-box

antenna at

30 GHz. This

antenna can

be considered

as

a linear antenna because of its relatively small aperture size in

one

direction (0.06 x 1.2 m). Consequently for this antenna the one-dimensional

Fourier transform relationship between the far-field spectrum and the

In figure 8 the relative power and phase of the far-field pattern measured in the H-plane is shown. The corresponding aperture field

.(relative power and phase), obtained by the method described in the previous section, is also given in figure 8. The horizontal scale of the aperture domain is 0.3 m/div (= 1 nanosec/div). A frequency span A of 21 GHz was selected according to formula 9.

From the aperture field distribution in figure 8 we see that the distance between the two gate markers is about 1.2 m. which is equal to the length of the aperture of the antenna.

Within these markers a significant nonzero field distribution is seen, which is the aperture field distribution of the antenna. The dip in the center of the relative power trace is due to the feed blocking over a distance of about 1.5 cm in the center of the antenna aperture.

In figure 9 the E-plane measurement results of the pill-box antenna at the same frequency are given for the situation that the feed was

excited by TE-modes. In the relative power of the far-field we observe

a flat topped main beam which is caused by a higher TE-waveguide mode

in the feed. In the aperture field distribution the effect of the overmoded feed is clearly visible. The transitions in the phase of the aperture field correspond to the small side lobes of the power

distribution of the aperture field.

Another experiment was performed with the pill-box antenna in order to demonstrate the ability of the aperture field analysis feature. Again the antenna was measured in the H-plane at 30 GHz (same situation as the results of figure 8), but now two pieces of absorber were placed in the aperture of the antenna as shown in figure 10.

As expected the measurement results show a distorted far-field pattern (compare with figure 8!). The power distribution of the aperture field contains two gaps at locations which correspond to the position of the two pieces of absorber.

Note that the values of the gate span and the marker indications in the aperture field results of figure 10 are about equal to the real dimensions.

5. CONCLUSIONS

It has been shown that the HP8510A mm-wave test system can easily be

configured to do antenna measurements with an acceptable dynamic range. However, dynamic range improvements are possible if harmonic mixers with a lower conversion loss are used in the system.

Further, it has been demonstrated that the time domain feature can be used succesfully to perform real-time aperture field analysis of an antenna. For instance, this can be used for fast fault detection of radiating elements of linear array antennas.

REFERENCES

[1] Procedures explained for rom-wave vector-measurements with the HP8510A

analyzer, Microwave Systems News, vol. 14, no. 13, Dec. 1984, pp. 65-90.

[2] HP8510 Network Analyzer Operating and Service Manual, Hewlett-Packard

Company, Santa Rosa, California, March 1984.

[3] Vokurka, V.Jo t Seeing double improves indoor range, Microwaves & RF,

vol.

24, no. 2, Febr. 1985, pp. 71-94.

ACKNOWLEDGEMENTS

The author acknowledges the supply of the rom-wave test set by

Hewlett

&

Packard Company. The author is grateful to M.B.M. Knoben

for his valuable cooperation during the experiments. This work was

Imixer

LO

signal

source

test antenna

•

signal

source

HP-IB

cantroller feed

---'

IF

mixer

network

analyzer

ai

b1

Figure 1. Simplified block diagram of the millimeter-wave antenna measurement system. . _

-LO

calibration

- - plane 2

output port 2

test

antenna

LO

CATR feed

cal1brat ion

Plan,;"1

-input port 1

input

Pi A Sll/M REF -S0.0 1

'V

MAO

___ L

,

-l---i----'---j--!.

I i i :

--~---

-

----~---r----r I i i ! -

-r" -.-

-i- ---

--i--

I

-,-_1-__

L __

L __

L _

J ___

J

START 26.500000009 GHz STOP 40.000000008 GHz

Figure 3. Noise level at the output port 2 relative to the power

level at the input port 1 (10 dB/division) for two

different averaging factors (128 and 2048).

powerl

I

I

I

I

-I

CATR

feed

spill

0/

CATR

efficiency

•

..

test

antenna

mixer

.. .. .. 'II . .

test zone test antenna conversion

efficiency efficiency

loss

Figure 4. Power flow model used to estimate the dynamic range

performance of the mm-wave test system.

I

I

output

•

dB A

\I

3.6279 dB ~--

--- -- i---f--+---I---1f----+--+----i---j

--- --- ---

--+--+--t---I---1--t----r--~

,

.... ~··--,-+---L--_j,_h--_tjlh

---~- I--;-~--;-'

I I , ~----'----'--- --

--'

-.-- r---j----_ i-35.000000000 GHz 39.000000000 GHz

Figure 5. Noise level measured at the output of the mixer relative to the power level where the 0.6 m parabolic reflector antenna receives maximum Signal.

I

\

-"- -"""

1\1\

IN

\r

J\

\.

_\

J

v

E-plane 'p"

_/1

f--,

:

,

!

[V

_\1':

I

,..r

I

[\t\

IAI

~

I

\,

IV"(

•

45 degr.-plane (copolar)

I"

\

~

I

_{II "\}

f\

t

r..,

~

\ I

J

\/\

/

"

~

J

:'-v,

V\

_1\

_V

_/

If

II

I

H-plane

:--~-r-~----r-~-

T

-~--- -~--- -~---

l

1--~ f I ' 45 degr.-pla~e (crosspolar)

/

I

,

I Figure 6.

The E-plane, a-plane and 45 degr.-plane (CQ- and crosspolarl radiation patterns of the 0.6 m parabollc reflector antenna at 3S GHz;

horlzonta!: angle (4 riegr/div)

- vertlcal rel. power (5 dB!div)

~

I(

"

1(\

""

~

r

\f\

\!\

v

"\

_V

(\

~

E- plane Ihp4'

r

L

~I

.A

)

1,-\

V\1I

(

_d\

J.f'1

'\

\/\

V

v

y

_V

,

T

\-45 degr.-plane (copo!ar)

/

...

..

J1'\ "'"Y\

1

~

Ii

_.Ii

'W

t,r\

I

t\

~

_.J

\

IAr

A

V

H-plane 45 degr.-plane {crosspo!arl

.1"1

fLY

Figure 7.

The E-plane, H-plane and 45 degr.-plane (co- and crosspolar) radiation patterns of the 0.6 m parabolic reflector

antenna at ]9 GHz:

- horizontal angle (4 degr!div) - vertical : reI. po~er (5 dB!div)

I ~

-J

)

!

f\

/I

)

1\

""

f'

,/"

V

tv

.~

1\

II

f

""

/'

l7

far f1eld

-

(rei. power and pahse)

p Ihp

1\

\

1\

~

(

_\

/

1\

/

\

1\

f-vv

1\

near-field ( rel. power and phase)

.J

\

WI

tv

V

_\

I!\

\

~

_h

/ \

1\

rl

V

N

\

1'\

\

\

\

.r'

/V

••

Figure 8.

The far-field and near-field radiation

characteristics of the 1.2 m pill-box

antenna (H-plane, f = 30 Gliz):

- horizontal ; angle (4 degr!div) or

distance (0.3 m/div)

- vertical reI. power (5 dB/div) or

phase (36 degr/d!v)

-CD

I

11

r.J

II;

(\

I

~

t' V

~

""'V

A

f>/""

I'

/

1""1

~

_If"'!

'.

I

)

':ar-field (rel. pow~r and phase)

hp Ihp

I'

1\

/

\

"'"

1"\

_If

v

~

ill

near-field (rei. power and phase)

---_

..

,,""

~---I

/

I

1/

\

'"

_~

1"-,

'"

~

II

~

,J

II

\JV

fN

\

'~

\

\

\

fmi

I'

Figure 9.

The far-field and near-fjeld. radiation

characteristics of the l.~ m pill-box

antenna (E-plane, f '" 30 Gil?):

- horizontal

- vertical

angle (-1 degr!div) or

dist3:";Ct: (0.3 m/div) rei. pC' .. 'er (5 dB/div) or phase '.36 degr!div)

~

1/

V

1\

fl

'\

1'-,

II

\

...

'-

L:1

'"

l

v

Vi

J"

I'

T\

JJ

/

v

I

V

far field ( _{reI. pOwer and pahseJ}

p Inp

il"

GAT

5

AN

.0 s

RIlf.

~,

• • • 0 •• m _1'1

1\

m

\

1/

\

_f-

\

J.

/

1\

l-near f~eld (reI. power and phase)

)

_~

/

I\L

./

lei.

V

I

1

~

,/\1

II "\

r\

f

V

~I V

IJ

IIbsorbsr

//

_{... \}

.1

_I-

_-llh4

si

II-15 1

4.

'2.

(all distances In em)

Figure 10.

The far-fieId·and near-field radiation

characteristics of the 1.2 m pill-box

antenna (H-plane, f = 30 GHz), while the aperture was blocked with two pieces of absorber:

- horizontal : angle (4 degr/div) or distance (0.3 m/div)

- vertical _{reI. power (5 dS/div) Or}

phase (36 degr/div) I" I I N o I

DEP.-\RTMEr-.T OF ELECTRICAL ENGINEERING

!:.inJ:ic)':cn l.:nivasity of Technology Research Reports (ISSN 0167-9708)

i 127! lla:ut;'n, A .. \.II., P.M.J. Van den Hof and A.K. Hajdasifiski

THE PACt: :-lATRIX: An excellent tool for noise filtering of Markov parameters, order testing and realization.

EUT Rep0rt 82-E-127. 1982. ISBN 90-6144-127-7 (12M} ~irola, V.F.

~IARKo\' L\.'.j ~IODELS OF A TRANSACTIO~AL SYSTEM SUPPORTED. BY CHECKPOINTlNG

AND RECOVERY STRATEGIES. Part I: A model with state-dependent p<lr<lrnei:er:>.

ruT Rep0rt 82-E-128. 1982. ISBN 90-6144- 1 28-5 (l':'Jj :,icol~, \ .. F'.

:·IARKOV I.!.:-.i HODELS OF A TRANSACTIONAL SYSTEM SUPPORTED BY CHECKPOINTING

."L'!) RECIWERY STRATEGIES. Part 2: A model with a specified number of

,:,lmpl..,t"d transactions bctween checkpoints.

{l31 i

El,l H<!P0rl 82-1::-129. 1982. ISBN 90-6144-129-3

TilE PAP Pm:;PROCESSOR: A prscompiler for a language for concurrent

;.ru<':"~~~:"J on iJ. multiproccs~or system.

BUT Rct:crt. 82-E-130. 1982. ISBN 90-6144-130-7

Eijnde~, P.M.C.~. van cen, H.M.J.M. Dortrnans, J.P. Kemper and

M.P.J. St.evens

JOBHAND~ A NETWORK OF DISTRIBUTED PROCESSORS.

EUT Repcrt 82-E-l)1. 1982. ISBN 90-6144-131-5

( l i t ; V"rli·jsr-j"nk, A.P.

')~) 1'UE .':'PPLlrATroN OF BIPUASE CODIl:G IN DATA COf1MUNICATION SYSTEMS. :::'1' R-,,;:-:-,!"t fJ2-E-132. 1982. ISBN 90-6144-132-3

(13,) ;:eljr:!.::'!~' C J.II. en B.II. van Roy

. ~::'I'!::jJ s:: 3EREKENEN VAN PARAHETERS BIJ HET SILOX-DIFFUSIEPROCES.

:.'i"!' Rer;·.;!·c ~3-E-133. 1933. ISBN 90-6144-133-1

(1141 :l.ut;'r, Th.G. van de and S.C. van SOr:Jeren Greve

A :·fETlI0D rOR SOLVING BOLTZMANN'S EQUATION IN SEMICONDUCTORS BY

EXP,\;.iS 10:·; IN LEGENDRE POLYNOMIALS.

ITT Report 83-E-134. 1983. ISBN 90-6144-134-X

(I 3.)} \·tll, H.t:. van de

TI'iE-OPTI~L\L CONTROL OF A CRANE.

~XT Hepon 8)-£-1)5. 1983. ISBN 90-6144-135-8

i I.h r:_~~r, C. <lud W.J. Eogers

:HE SCHULER PRINCIPLE: A discussion of somc facts and misconceptions. En Rerun 83-E-136. 1983. ISBN 90-6144-136-6

(13]" ~2.3.1der. J.E. and E.F. Schreurs

~PHENOMENA IN HIGH VOLTAGE FUSES.

El~ Report 83-E-137. 1983. ISBN 90-6144-137-4

Coden; TEUEDE Eindhoven UniVersity of TechnologY Research Reports (ISSN 0167-9708):

(138) Nicola, V.F.

A SINGLE SERVER QUEUE WITH MIXED TYPES OF INTERRUPTIONS: Application to the modelling of checkpointing and recovery in a transactional system.

EUT Report 83-E-138. 1983. ISBN 90-6144-138-2 (139) ~, J.G.A. and W.F.H. Merck

TWO-DIMENSIONAL MHO BOUNDARY LAYERS IN ARGON-CESIUM PI~SMAS. EUT Report 83-E-139. 1983. ISBN 90-6144-139-0

(140) Willems, F.M.J.

COMPUTATION OF THE WYNER-ZIV RATE-DISTORTION FUNCTION. EUT Report 83-E-140. 1.983. ISBN 90-6144-140-4

(141) lIel.lvel, W.M.C. van den and J.E. Daalder, M.J.M. Boone, L.A. II. Wilmes INTERRUPTION OF A DRY-TYPE TRANSFORMER IN NO-LOAD BY A VACUUM CIRCUIT-BREAKER.

EUT Report 83-E-141. 19B3. ISBN 90-6144-141-2 (142) Fronczak, J.

DATA COMMUNICATIONS IN 'I'm: MOBILE RADIO CHANNEL. EUT Report 83-E-142. 1983. ISBN 90-6144-142-0 (143) Stevens, M.P.J. en M P.M. van Loon

EENlMULTIFUNCTIONELE I/O-BOUWSTEEN.

EUT Report 94-E-143. 1984. ISBN 90-6144-143-9 (144) Dijk, J. and A.P. Verlljsdonk. J.C. Arnbak

D"IGiTAL TRANSMISSION EXPERIMENTS luTifTHE ORBITAL TEST SATELLITE. EUT Report 84-E-144. 1984. ISBN 90-6144-144-7

(145) Weert, M.J.M. van

MINIMALISATIE VAN PROGRAMMABLE LOGIC ARRAYS . EUT Report 84-E-145. 1984. ISBN 90-6144-145-5

(146) Jochems, J .C. en P.M.C.M. van den Eijnden

'IOES'I'AND-'roEmJZJN; IN SE(!IJENI'IELE CIlOJITS.

EUT Report 85-E-146. 1985. ISBN 90-6144-146-3

(147) Rozendaal, L.T. en M.P.J. ~, P.M.C.M. van den E1jnden DE REALISATIE VAN EEN MULTIFUNCTIONELE I/O-CONTROLLERIMETlBEHULP

~N EEN GATE-ARRAY.

EUT Report 85-E-147. 1985. ISBN 90-6144-147-1

(148) Eijnden, P.M.C.M.

A <:x::lJRSE CN FlEW PR:GRAMMMll..E I..CGIC.

EUT Report 8S-E-148. 1985. ISBN 90-6144-148-X 1149) Beeckman, P.A.

MIT.LIMEI'ER-wAVE ANTENNA MFASUREMENTS WITH THE HP8510 NElW)RK

ANALYZER.